ABSTRACT

In this paper we investigate the power allocation optimization for spectrum efficient multi-pair two-way massive MIMO (TWMM) amplify-and-forward (AF) full-duplex (FD) relay over Ricean fading channels, where multiple user-pairs exchange information within pair through a AF-FD relay with very large number of antennas, while each user equipped with a single antenna. First, the zero-forcing reception/zeroforcing transmission and maximum-ratio combining/maximum ratio transmission processing matrices with imperfect channel state information at the relay are presented. Then, the unified asymptotic signal-to-interference-plus-noise ratio (SINR) expression of the system at general power scaling schemes are investigates. Finally, the joint user-relay power allocation (JURPA) scheme is proposed to improve the spectral efficiency of TWMM-AF-FD relay system. Simulation results show that the proposed JURPA scheme outperforms traditional user-side only power allocation scheme.

Keywords:

Massive MIMO, Ricean Fading Channels , Processing Matrices, Power Allocation

1. Introduction

The ever growing challenges for significant traffic growth driven by mobile Internet and Internet of things have made system capacity enhancement one of the most important features in next generation wireless communication systems. The general consensus is that the aggregate data rate will increase by roughly 1000X by 2020. Massive multiple-input multiple output (MIMO) [1] is identified as one of the key enabling technologies to achieve this goal due to its strong potential in boosting the spectral efficiency (SE) of wireless networks [1] [2].

The term massive MIMO indicates that the base station (BS) or relay employs a number of antennas much larger than the number of active data streams per time-frequency resource. Massive MIMO was originally designed for time division duplex (TDD) system [1]-[7], since by exploiting the channel reciprocity in TDD setting, the required channel state information (CSI) for downlink transmission at the BS can be easily obtained via uplink training [1]. The training overhead scales linearly with the number of user equipments (UEs) and is independent with the number of BS antennas. As frequency division duplex (FDD) dominates the current wireless cellular systems, the application of massive MIMO in FDD system is even more desirable. In FDD massive MIMO, the downlink training and corresponding CSI feedback yield an unacceptably high overhead. One attempt of practical FDD massive MIMO is called joint spatial division and multiplexing (JSDM) [8], where the correlation between channels is exploited to reduce the training and feedback dimensions. Another scheme is called beam division multiple access (BDMA) [9], which gets rid of the need of CSI at transmitter and provides strong potential to realize massive MIMO gain in FDD system.

In TDD and FDD massive MIMO systems (namely halfduplex (HD) massive MIMO systems), the uplink and downlink UEs must be allocated with orthogonal time slots or frequency bands, which results in insufficient utilization of time-frequency resources. Inspired by the recent development of full-duplex (FD) communication [10], co-time co-frequency uplink and downlink (CCUD) trans- mission becomes another option in the cellular system. Although attractive in SE, CCUD transmission is considered challenging due to the strong self interference (SI) caused by the signal leakage between BS/relay transmitter and receiver, especially when the BS is equipped with large-scale antenna arrays. To support the CCUD transmission, the BS employs a separate antenna configuration where two separate large-scale antenna arrays are used for transmission and reception, respectively [11]. In this case, the downlink channel reciprocity is commonly considered as unavailable [12]. Without reciprocity, the training overhead to obtain the downlink CSI scales linearly with the number of BS antennas, which poses another big challenge.

Note that the CCUD transmission in the cellular system with massive MIMO BS/relay has been investigated recently in several works (See [13] [14] [15] and the references therein). The authors in [13] studied the SE performance of CCUD transmission in both macro-cell and small-cell environments. The linear beamforming design of the BS for CCUD transmission has been considered in [14]. The power allocation scheme for user-side only has considered in [15] to optimize the system spectral efficiency.

In this paper, we investigate the power allocation optimization for spectrum efficient multi-pair two-way massive MIMO (TWMM) amplify-and-forward (AF) FD relay over Ricean fading channels. The unified asymptotic signal-to- interferenceplus-noise ratio (SINR) expression of the system based on the be- amforming matrixes of MRC/MRT and ZFR/ZFT at the relay, at the power-scaling (,and are fixed) are investigates. Moreover, the joint user-relay power allocation scheme is proposed to improve the spectral efficiency of TWMM-AF-FD relay system.

Notation:;;;; to denote the transpose, conjugate-transpose, conjugate, inverse and the trace of. respectively. denotes an identity matrix. is the expectation operator, repre- sents the Euclidean norm.

2. System Model

We consider the user-pairs two-way AF relay system, where pairs of single-antenna users on two sides try to exchange information within pair through a massive antenna relay (R) with antennas, as is illustrated in Figure 1. Without loss of generality, a pair of source nodes and are too far apart to communicate directly. Meanwhile, one source can be inevitably interfered by others on the same side.

2.1. Channel Model

Let and denote the channel from all users transmit antennas to relay R receive antenna array and the channel from the relay R transmit antennas to all users receive antennas, respectively. Specifically, and can be expressed as and, is the channel matrix representing fast fading and is the diagonal matrix representing large-scale fading with, . The fast fading matrix can be written as [4],

, where is a

Ricean K-factor diagonal matrix with. contains the independent identically distributed (i.i.d.) entries. denotes the deterministic component, and let, where denotes the arrival angle

of the k-th user, is the wavelength, and is the antenna spacing. For convenience, we set.

Let denote the echo interference (EI) channel matrix between the relay transmit and receive arrays with (i.i.d.) elements. and represent the self-loop interference coefficient at and the inter-user interference channel coefficient from to. or denotes the set of users on the same side. and can be modeled as i.i.d and random variables.

2.2. Channel Estimation and Data Transmission

Since it is impossible for the relay to obtain the complete channel state information from all the channels, so it is necessary to estimate the channel matrix. For the Ricean fading channel model, the Ricean K factor matrix and the LOS transmission signal component are fully known in the relay and the user. So we only need to estimate and, since and are i.i.d, we can use minimum mean square error (MMSE) estimator. Let be the length of the coherence interval and let be the number of symbols used for uplink pilots. In the training part of the coherent interval, all users receive and transmit antennas simultaneously send symbols of length to the relay.

The received pilots matrices at the R’s receive and transmit antenna arrays are given by and, among them. are pilot sequences transmitted from all users transmit antennas and all users receive antennas, respectively. is the channel matrices from all users transmit antennas to R’s transmit antenna array and is from all users receive antennas to R’s receive antenna array. and are additive white Gaussian noise (AWGN) matrices with (i.i.d.) elements. And is the transmit power of each pilot symbol. All pilot sequences are assumed to be paired and distributed independently, and () where. This requires. and we set in this paper. We consider the LOS component assumed to be known and can be removed, the remaining terms of the received matrices are, and

. The MMSE estimate of and are

and

.

According to MMSE estimates, the actual channel can be expressed as and, () and () denote the available channel estimate and estimation error, respectively. The elements of the i-th column of and are RVs with zero means and variances and where. In addition, due to the nature of MMSE estimates, is independent of and is independent of.

At time instant t, all sources transmit their symbols to R and R forwards the amplified signal to destinations. The received signals at the relay and the k’th user are given by:

. (1)

. (2)

where and, denotes the transmit vector of R. and represent the noise vector at R and. the elements of and are assumed to be (i.i.d.) and.

The transmit vector of R at time instant t can be expressed as:

(3)

where is the beamforming matrix, and denotes the processing delay at R. In this paper, some loop interference cancellation methods [16] can be adopted at the relay before carrying out (3), so we can regard the residual loop interference at R as additional noise. So, we replace in the loop interference term in (1) by a Gaussian noise source with the same power limitation to represent the residual loop interference signal. Then (2) can be expressed as:

(4)

3. Beamforming Design and SINR Anlysis

In this section, we introduce the ZFR/ZFT-based and MRC/MRT-based beamforming design, the end-to-end SINR of the proposed transceiver schemes for multi-pair two-way MM-AFFDR system are analyzed.

Lemma 1: By the law of large numbers, if is large enough, the inner product of any two columns in the estimate channel matrix can be expressed as [17]:

(5)

and

(6)

According to Lemma 1, it can be easily obtained that:

(7)

and

(8)

3.1. ZFR/ZFT Beamforming

The ZFR/ZFT beamforming matrix can be expressed as [18]:

(9)

where,. is the amplification

factor, which can be expressed as:

(10)

where is a pair of user.

Theorem 1: Using ZFR/ZFT beamforming matrix with imperfect CSI from MMSE estimation, the end-to-end SINR at the k’th user can be expressed asym- ptotically (in M) as:

(11)

the power for channel estimation error and power for echo interference can be expressed asymptotically (in M) as:

(12)

Using ZFR/ZFT beamforming matrix with imperfect CSI from MMSE estimation, at the power (), the asymptotic SINR when can be expressed as:

(13)

3.2. MRC/MRT Beamforing

The MRC/MRT beamforming matrix can be expressed as [18]:

(14)

where,. is the amplification

factor, which can be expressed as:

(15)

Theorem 2: Using MRC/MRT beamforming matrix with imperfect CSI from MMSE estimation, the end-to-end SINR at the k’th user can be expressed asym- ptotically (in M) as:

(16)

the power for channel estimation error and power for echo interference can be expressed asymptotically (in M) as:

(17)

Using MRC/MRT beamforming matrix with imperfect CSI from MMSE estimation, at the power (), the asymptotic SINR when can be expressed as:

(18)

Specially, when, the deterministic equivalent for of ZFR/ ZFT becomes the same as that of MRC/MRT.

4. Spectral Efficiency Optimization by Power Allocation

In the previous sections, we have assumed that all the sources and relay use the same transmit power. However, the spectral efficiency achieved in reality may not be optimal since each source-destination pair suffers from different fading environments. As a result, power control scheme at sources and relay is need to improve the system performance and optimize the SE subject to the maximum power constrains at and at R. The SE is defined as:

(19)

For convenience to analysis, we rewrite the end-to-end SINR in Theorem 1, 2 under ZFR/ZFT and MRC/MRT beamforming schemes as a unified expression as:

(20)

For ZFR/ZFT beamforming scheme, we have:

(21)

For MRC/MRT beamforming scheme, we have:

(22)

The SE optimization problem can be written as (23). By introducing auxiliary variables, (23) can be written as (24).

(23)

(24)

Since the target function is not in the posynomial form, the similar method in [19] for solving geometric programming (GP) can be used. For any, can be approximated by a posynomial function near, where,. Then the SE optimization problem can be solved by using several GPs, Algorithm1 is in the following description.

5. Simulations Results

In this section, we examine the SE of the multipair two-way MM-AF-FDR system when its uplink power and downlink power are distribution at the same time. Without loss of generality, we let, and all users have the same Ricean K-factor. Under such assignments, the asymptotic SE of MRC/MRT and ZFR/ZFT are equal. Then we let, ,.

Figure 2 shows the SE v.s.. We can see from Figure 2 that the achievable SE is improved significantly by using the proposed JURPA scheme, which optimize the uplink power and downlink power at the same time. Compared with the user-side only power allocation scheme in [15], the proposed JURPA scheme can obtain significantly SE improvement, and the SE gain increases with the decreasing of.

Figure 3 shows the SE v.s. the number of the relay antennas. The proposed JURPA scheme obtains the optimum SE performance when compared with the user-side only power allocation scheme in [15] and the no power allocation scheme. The SE performance of TWMM-AF-FD system with ZFR/ZFT beamforming outperforms MRC/MRT beamforming.

Figure 4 shows the SE performance v.s. It is seen from Figure 4 that the proposed JURPA scheme outperforms the userside only power allocation scheme in [15] and the no power allocation scheme on the system SE performance. Moreover, the SE gain increases with the increasing of.

6. Conclusion

In this paper we investigate the power allocation optimization for spectrum efficient TWMM-AF-FD relay over Ricean fading channels. First, the ZFR/ZFT and

MRC/MRT processing matrices with imperfect channel state information at the relay are presented. Then, the unified asymptotic SINR expression of the system at general power scaling schemes are investigates. Finally, the JURPA scheme is proposed to improve the spectral efficiency of TWMM-AF-FD relay system. Simulation results show that the proposed JURPA scheme outperforms traditional user-side only power allocation scheme.

Acknowledgements

This work is supported by Jiangsu Province Natural Science Foundation under Grant BK20160079, National Natural Science Foundation of China (No. 61671472, 91438115, No. 61371123).

Cite this paper

Wu, C.Y., Yue, T., Xu, K. and Xie, W. (2017) Power Allocation Optimization for Spectrum-Efficient Multi- Pair Two-Way Massive MIMO Full-Duplex Relay over Ricean Channels. Int. J. Communications, Network and System Sciences, 10, 35-47. https://doi.org/10.4236/ijcns.2017.108B005

References